This miniature receiver is based on a design I created in 1987; it was the first super regen set that was easy to use and had decent sound quality. It did have a particularly bad shortcoming in that its performance dropped off severely at the low end of the VHF broadcast band. In 2002, I wanted a small FM receiver to use as a portable. Remembering the simplicity of my earlier design, I reconstructed it and solved that shortcoming. Additionally, I elaborated on it so that the RF amp would perform as an audio stage to drive headphones; i.e. reflexing. Current consumption of my new receiver is low with the B+ drawing about 3mA. Heater current is .15A or .3A depending if the 12AT7 heater is wired for 6 or 12V. Battery operation is therefore practical, so I also made up a vibrator supply to run the whole set off a 6V 8A SLA battery. Since the SLA battery has failed after 20+ years, the circuit was modified to take a NiCd type. Total consumption at 6V is about 600mA, so even dry cell operation could be contemplated for short periods of time. The B+ drain is low enough to give reasonable life out of 15 nine volt batteries in series. In that case the 6V battery would only need to supply 300mA, which is about the drain of a torch bulb.
See notes regarding the 15uH chokes.
The heart of the receiver is the right
hand side triode. This is the super-regen detector. By means of the cathode
choke, and the internal grid and cathode capacitances, this triode oscillates
at whatever frequency the grid circuit is tuned to. This is the same frequency
as the station we wish to receive. Grid leak bias is obtained from the
330K and 33pF in the grid circuit. The coil is 4 turns of 18 gauge tinned
copper wire, air cored with diameter of 10mm.
For the tuning condenser, a 15pF unit is the best choice, but as I've got a few MW broadcast units with a 100pF oscillator section, I used one of those with a 33pF series condenser to give complete coverage of the 88-108Mc/s band.
So far, we have a VHF oscillator, but in order to super-regenerate, it needs to go in and out of oscillation at a supersonic rate. The grid RC network values are chosen for this so the valve cuts off after a certain time, whereupon oscillation recommences. See the Fremodyne article for more info about super-regen operation.
My breakthrough with this receiver design was with the regeneration control. The usual way is to vary the B+ to the detector. For most sensitivity, the detector is adjusted so that it has just started to oscillate. However, I found sensitivity and sound quality to be very poor towards the 88Mc/s end of the band. Examining the quench waveform on the CRO revealed how obvious it was. I suppose more by accident than anything else, I discovered that by taking the grid more negative to control regeneration, the performance picked right up, and performance was consistent right from 88 to 108 Mc/s. I also noted that the variable B+ type of regeneration control had little effect, so it was dispensed with. Instead, making the negative grid supply variable gave far more control.
The B+ supply was found to be optimum around 157V. Likewise, the grid supply needed to go up to about -30V. However, these figures are not carved in stone, and will and do vary for other clones of this receiver. For instance, in one receiver I found the B+ should be 140V. The regeneration control should be able to cut the oscillation off altogether; if not increase the -30V supply or reduce the B+.
Note that the supply shown on the circuit is 180V. This is between the B+ and B- terminals. Back bias is used, meaning there's a 30V drop across the 10K resistor from B- to earth. This provides the -30V supply. The plate supply is still 150V. (180-30)=150.
While the aerial can be connected directly to the 4.7pF input capacitor, some problems arise by doing this. Firstly, loading by the aerial can cause the oscillator to be unreliable, stop oscillating, and go off tune. This is a major problem especially for a portable set, as you can imagine the aerial is going to be shifted around, moved near other objects, etc. Secondly, the oscillation from the super regen detector will be radiated by the aerial. In my opinion that isn't a problem...who cares if other receivers are interfered with...it's the one you're listening to that counts isn't it?
A grounded grid RF stage is used here. Although it has hardly any gain, it's stable, can be untuned (avoiding annoying two gang tuning condensers and getting them to track), and has excellent isolation.
The cathode and plate loads are RF chokes. Aerial signal is fed into the cathode via 1000pF, so as not to upset the bias if the aerial has DC continuity to earth. The grid is RF bypassed also by 470pF.
From the triode plate, the signal proceeds into the above mentioned 4.7pF condenser.
The value of the RF coupling condenser should be as large as possible to transfer maximum signal into the detector without it becoming difficult to oscillate. 4.7pF seemed to be about right.
Reflexing and the Audio stage
Not mentioned so far, to avoid confusion, is how the RF stage also functions as the audio amplifier.
In the normal way of things, another stage of amplification would be needed to drive headphones from the detector triode. However, we can make dual use of the RF amplifier stage instead! Because audio frequencies are so far apart from VHF we can amplify both and keep their paths separate.
Let us now examine how this is done in detail. For the audio signals, the left hand triode functions as a normal grounded cathode stage. The audio signal from the 56K detector plate resistor is fed into the 1M volume control in the usual way, with the wiper then feeding the grid on the other half of the 12AT7.
As well as keeping the grid at earth potential, as far as RF is concerned, the 470pF also bypasses more of the quench signal that is still present in the detected audio, but such a low capacitance does not bypass the audio due to the lower frequency components.
In series with the plate supply is the output transformer. This has no effect on the DC conditions of the triode functioning as an RF amplifier, but because 1000pF is not a very high value of capacitance at AF, the audio signal can pass through into the transformer and drive the headphones. The plate choke is such a low inductance at audio frequencies it has no effect.
Bias is obtained with the 1K cathode resistor. Again the RF choke has no effect at audio due to its low reactance. Cathode bypass is effected by the 1000pF for RF and 25uF for audio. Electrolytic condensers are poor at RF, hence the inclusion of the ceramic bypass.
The speaker transformer I used is a N.O.S replacement for an AWA P1portable TV. As far as I can determine, it has an impedance ratio of about 8K to 15R. It is not critical. For more efficiency, the plate winding should be of higher impedance. A 100V PA speaker transformer is a good choice with the 10K or greater tap selected. There is no reason why ordinary high impedance phones cannot be used instead, eliminating the transformer altogether. If you do this, watch the polarity, or the phone magnets will lose their strength, and make sure that their insulation is up to the 140~180V this receiver operates off. The application of 180V to the listener's head would result in a rather interesting facial expression don't you think?
Anyone capable of building this would be able to work out what ratings of the resistors & condensers are. Suffice to say, use ceramics for all the RF bits, and electros for the B+ and audio cathode bypass. The .01 volume control coupling should be polyester or polystyrene, or a decent ceramic that doesn't leak...designers of those red topped Ducons take note! To be realistic, you will get away with 100V rated ceramics in this circuit even though some might have ~150V across them. Obviously with only 3mA current consumption, all resistors can be 1/4W.
The RF chokes.
In my first few constructions of the 12AT7 receiver, I used a 15uH choke wound on a ferrite core. These were once available from the now defunct Dick Smith chain of electronics stores. This particular type of choke worked well, but it eventually became unavailable. Other 15uH chokes of the axial type were tried but did not work. The answer was to use a home made choke. This is simply 75cm of 25B&S enamelled copper wire wound on a 6.5mm plastic tube. 75cm represents a quarter wavelength at 100Mc/s, and thus has its highest impedance in the FM band. It was found the home made choke performed much better and is to be recommended instead of the originals, even if they were still available.
Some constructors have noticed that the home made choke has a lot less inductance than 15uH. In fact it's closer to 2uH. This is nothing to be alarmed about as the method of operation is different. See the notes here.
Note that if oscillation seems poor, the connections to the choke may need to be reversed. This is because of magnetic coupling to the tuned circuit. If the coupling is in the wrong direction, it will cause negative feedback, and thus a reluctance to oscillate.
For the tuning condenser you can take the
easy way out and use varicap tuning, but you'll need a regulated supply
and the current consumption is added to. A good varicap diode is the BB105.
The best regulator for varicap tuning is the Philips TAA550 IC which is
like a very stable 33V zener diode. See the notes on the Model
T Ford car radio if you want to use varicap diodes.
I prefer using a proper mechanical variable condenser as it has a higher Q and has less drift problems.
See also my notes on the Fremodyne. The resistor values that shouldn't be departed from are the 56K plate resistor, the 3.3M and 330K grid resistors, and the 1M volume control. For the condensers, don't change the 1000pF bypass on pin 6, or the 33pF on pin 7. Otherwise, near enough is good enough. If quench frequency is too low, as evident by a beat with the stereo subcarrier, change the 330K to 270K.
Only do this if necessary because raising the quench frequency reduces sensitivity. If this is done, it's possible the -30V regeneration supply will have to be increased to compensate for the reduction in grid resistance.
Vibrator Power Supply
For portable operation I have used
a conventional non synchronous vibrator inverter. The transformer is a
conventional 12.6V CT 300mA to 240V unit which is cheap and easy to get.
The transformer feeds a bridge rectifier to provide the DC for the receiver. The 8.2K drops the voltage to about 180 as well as providing filtering. Of course you could use a proper vibrator transformer with centre tapped secondary, allowing a synchronous vibrator to be used. However, it will need to be of the split reed type to allow the back bias to be created.
The vibrator I used is a Plessey 614.
The buffer condenser suited my particular transformer; you will need to check for yours. See the extensive notes on vibrator power supplies elsewhere on this site for more information. The buffer is selected for the correct waveform across the transformer primary (i.e. the 12V CT winding). If you have no CRO, the next best way is to select the value that gives minimum current consumption at 6V with no load on the supply. This should be coincident with no contact arcing. Note that the voltage rating should be at least 630VDC for this condenser.
The 100R resistors from each contact to earth were to reduce the RF interference by damping any spikes from the primary winding. It is good design practice to include these resistors even if no RFI is evident, in the interest reducing any spikes the contacts may be exposed to. It is also important to remember not all interference suppression measures will work for one vibrator supply as they do for another.
I used a pair of 6V 4Ah sealed lead acid batteries originally, but now a 7.2V 4Ah NiCd battery has been installed. It consists of two lots of 3x D size cells in heatshrink wrapping. 6V would have been electrically more convenient, however I used what's to hand, and a1R resistor drops the excess voltage so the valve heater and inverter receive their intended 6V.
The charger circuit has been modified to operate with the NiCd battery and is now as shown. NiCd cells are meant to be charged at a constant current (usually 1/10 of cell capacity), and then the charge terminated to prevent damage. The problem is knowing when the charge has completed. A complicated circuit can detect a dip in voltage which occurs just as full charge is reached, but that's getting too complex for this application. It is safe to continuously charge at the so called "trickle" rate which is 1/100 of cell capacity, which in this case is 40mA.
The way around the problem used here is to almost fully charge the cells at their 1/10 rate, and finish off with a continuous 1/100 rate.
The LM317 provides 8V, which corresponds to 1.3V per cell, which is what the voltage level is close to full charge. A 12V 18W lamp limits the charge current to about 400mA. Once the cells have come up to 1.3V, the trickle current is now determined by the 82R resistor. Diodes prevent the battery discharging into the regulator circuit if the 12V supply should be removed.
In the case of the SLA battery, things are a lot easier. No trickle charge circuit is needed or desirable, and the LM317 resistors were simply configured for 7V at the cathode of the 1N5404 with no battery connected.
The lamp actually consists of a pair of 12V festoon bulbs in parallel. Even though they were marked as being 18W each, they actually measured half this. Hence, two in parallel give 18W.
A 5K pot is used to vary the bias in the
usual way. The 25uF is to bypass the audio and quench component while the
1000pF bypasses the RF. The bottom end of the RF choke is therefore earthed
except for DC which is variable from 0 to 3V. As far as receiver performance
goes, there is no deterioration in sensitivity or sound quality from modifying
the control thus. What did become evident was a slight time lag from when
the regeneration control was adjusted to when it took effect. It's only
a fraction of a second but it's noticeable. If that is not of concern,
then by all means use this method of control. My guess is that it's the
time constant created by the 5K pot and 25uF that cause this characteristic.
This circuit has the advantage of eliminating the C- supply and does not
add to the current consumption. There is also a degree of automatic stabilisation
by virtue of the current feedback. This method of stabilisation is actually
used in the Fremodyne receiver. It will be found that for receiving most
stations, the control can simply be set at the low end of the band and
Postscript May 2008: After work on the Model T Ford car radio, and other variations of this receiver, it became clear that this is the preferred kind of regeneration control. As it turned out, the 25uF was unnecessarily high and 1uF is sufficient. There is no time lag problem then. It was also found a 10K is usually necessary, possibly shunted with another resistor to spread out the adjustment over the pot's full rotation.
The next circuit is shown only to illustrate another method I tried, but it is now superfluous:
To improve upon the "time lag" effect (when
using a 25uF bypass capacitor), it would seem necessary to reduce the cathode
resistance or decrease the bypass. It was thought that the latter is not
acceptable as the performance might be severely compromised. So, we use
a lower value of pot, and put extra current through it to get the 0 to
3V voltage range:
While this works, it is no longer recommended. The 15uH value specified for the RFC is no longer relevant.
The maximum resistance now seen by the
cathode is 1K. However, the current consumption is now increased by the
47K/1K voltage divider, which consumes 3.1mA. So, the total receiver consumption
is now about 6mA. This is not a problem for receivers operating off the
mains or a car battery, but it is a waste of current as far as dry battery
operation for the B+ is concerned. The control works a lot better
however in that the time lag is less noticeable.
Given a choice, the original method of control with the -30V C- supply does give the smoothest control. In any case, the receiver performance is not ruined by any of the three circuits so far described. Postscript May 2008: After developing the later tuners it has become obvious that this circuit is unnecessary. While it works perfectly well it adds to the current drain and uses one unnecessary component (the 47K). It does not offer any automatic stabilisation as does the previous circuit.
The heater (or A supply) can come from
4 D cells or a 6V lantern battery. This will give about the same life as
it would powering a torch. More batteries in parallel will increase the
life before replacement necessary. The standard carbon zinc 6V battery
(e.g. type 509) has about 5Ah, so expect about 10 hours in the real world.
Of course, if NiCd cells are used, you'll need five in series to get 6V.
More efficiency would be gained by wiring the 12AT7 heater to 12.6V and using 8 D cells (or two lantern batteries) in series. This means only 150mA heater current so the internal resistance of the battery has less effect.
Looking at the B+ supply for this circuit, there are 15 x 9V batteries in series, giving 135V. By connecting the negative end of this battery bank to the A+, we get another 6V for free, so the total B+ is 141V. You may need to add or remove a 9V battery to get the correct B+ for your particular receiver. If the regeneration control cannot take the super regenerator to cut off, reduce the B+ until it does. You shouldn't have to go much below 140V.
The regeneration control shown uses a 1K pot as per the third method, but instead of providing it with 3V from the B+ using a 47K resistor (and thus wasting 3mA), we get the 3V from the 6V supply via a 1K resistor instead. The 3mA drain from the A+ battery is insignificant. As mentioned previously, this is no longer the preferred method of regeneration control.
Note that the power on/off switch is only in series with the heater battery. A second switch is not needed for the B+ battery, as no plate current will flow with the heater not energised. However, if you don't like the effect of the radio slowly dying as you turn it off, then use a double pole switch and cut off the B+ as well.
The sensitivity is higher than the Fremodyne. I'm using my set with two telescopic aerials of the TV kind. From my home in the Blue Mts, I can easily get all the Sydney, Wollongong, and Gosford mainstream stations with minimal noise. Distances are typically 80-100km or more. Quite a few community stations are receivable but with noise. I can get 2ST from the Southern Highlands with quite a bit of noise as well as some Newcastle stations. Taking it in the car from the Blue Mts. to Bendigo, I was able to receive stations all the way. Shepparton's 3SR was receivable well over the border into NSW.
How the receiver is tuned and the regeneration control is operated has a huge bearing on the maximum sensitivity. Remember that slope detection is being used for FM, so the receiver can never be tuned to the centre of the carrier where max. sensitivity, and least noise occurs, (one disadvantage of the super regen approach on FM). This is why the receiver will work much better on AM.
However, to get every last microvolt out of this set, tune to the carrier centre as close as you can without intolerable distortion and adjust the regen control to the point where oscillation almost cuts off.
At this point the two controls will interact slightly so repeat the operation.
Sound quality can be quite good (despite what the textbooks say, a correctly designed slope detector can give Hi Fi quality), especially on stronger stations with no noise. As usual there's the dreaded SCA & stereo subcarrier beat evident on some stations. You won't see that mentioned with most articles describing super regen sets for broadcast FM. Again, see my Fremodyne article about this. With this receiver, the regeneration control can be used to great advantage as it also controls quench frequency. This means it's often possible to find a point where the beat is least annoying or gone altogether.
As SCA has largely been replaced by internet and/or satellite streaming, reception of FM stations with super regenerative receivers is a lot easier than it used to be.
So you want to modify the circuit?
First it needs to be made clear that super regenerative receivers, and VHF circuitry in general is very critical. There has been a considerable amount of work to get this design to work right. If you want to change the critical parts of the design, I suggest you build the original circuit first so you know how it performs, and can judge the performance of an alterations from that. I do not recommend other valves. Although there's plenty of other VHF valves, the 12AT7 is what this circuit was designed for.
As to construction, forget the method of building MW sets with long wires all over the place and built on a piece of wood. A proper groundplane is essential and connecting wires must be short. We are dealing with frequencies 100 times greater than the MW band and things become very critical. If you can't make an aluminium chassis, then use one of the commercially made aluminium boxes to build the receiver in. If you don't mount the tuning condenser rigidly, you will find the receiver a real pain to tune. You might care to do some calculations, working out the inductance of a few cm of wire and then see what the reactance is at 100Mc/s. Virtually all of the problems encountered by others duplicating the VHF receivers on this site, have been to do with earthing and layout.
As for the commonly asked question as to how to change the frequency range of this receiver, it's easy; as with any LC tuned circuit, reducing inductance in a tuned circuit raises the frequency, and vice versa.
Practically speaking, if you want to make the receiver tune higher than 108Mc/s, (e.g. for aircraft band reception) take turns off the coil.
To make it tune lower, add turns. With my original 12AT7 receiver I designed back in 1987, I did get up to about 210Mc/s. However, having said that I can't guarantee the performance; you might have to optimise some of the component values by trial and error.
6ES8 I thought I'd just try this twin triode frame grid valve given its higher gain over the 12AT7. It's pin compatible except for the heater connections; the 6ES8 only being suitable for 6.3V. Performance was poor compared to the 12AT7, with low sensitivity, and the ratio of quench waveform to audio signal was very poor. Having said that, I did not modify the 12AT7 circuit except for changing the heater connections. However, this is not the first time I've used a 6ES8 in a super regenerative circuit. Previous attempts were not very good when using it in a self quenched circuit. I have had more success with the 6ES8 in a separately quenched receiver. The 6ES8 also performs well in a standard regenerative VHF receiver.
Voltage I've found that the specified 140-150V may not actually be necessary. With the 12AT7, performance appeared to be satisfactory down to about 80V. With the 6ES8, down to about 40 volts still allowed the receiver to operate. So, this could be good news for those who want to make the battery powered version.