The Pulse Counting FM Receiver

 Most constructors have never have heard of this type of receiver, unless you're into top end FM tuners, or you have read British electronics magazines from the mid 50's to the 1970's.
I first saw the design in a mid 1960's Practical Wireless magazine and due to the simplicity I thought it wouldn't work. How wrong I was! This was in 1990 when I was getting frustrated with the limitations of super regenerative receivers, prior to the development of my 12AT7 circuit, and was looking for other approaches to the 'simple FM receiver' problem.

Concept of Operation.
The pulse counting FM receiver is a superhet receiver, but differs from conventional FM receivers in two ways. First, the VHF signal is converted to an IF of 200Kc/s instead of 10.7Mc/s. This is because instead of a ratio detector or quadrature detector, a pulse counting detector is used. Its operation requires a low IF. Because of the low IF, no tuned circuits are required, except one for the local oscillator/RF input. This dispenses with the necessity to perform any alignment. Beyond the converter, all stages are resistance capacitance coupled.
Commercially made Pulse Counting receivers are a bit more elaborate than this. They're often dual conversion, with a conventional 10.7Mc/s IF which is then converted down to the ~150Kc/s IF with a crystal locked converter. This is done to prevent image response. These days, they often use a digital type pulse counting detector which provides good noise immunity. By passing the squared waveform through a Schmitt trigger, most of the noise will be removed.
However, for the homemade type of receiver, we don't need to go to such lengths to get a good quality receiver.

The earliest mention of pulse counting techniques appears to be in the early 1940's where such a receiver was used to monitor one of the first FM transmitters on the Empire State building. It used 807's for the RC coupled IF stage (a bit of overkill) and a 6H6 detector.
The next mention appears in Wireless World in the late 1940's when Thomas Roddam asks, "Why align FM discriminators?" and puts forward a pulse counting detector design. Then in 1956, M.G. Scroggie answers the question with a complete and practical Pulse Counting receiver. It was this design that provided the basis for subsequent valve receiver circuits until solid state versions appeared.

Once I had familairised myself with the operation of this method of FM reception, I settled on a basic design which has been used in all my receivers with minor variations.
I have built five such receivers up to the present time and all worked first time, with nothing to align. Other constructors who have read this article have also duplicated the design with excellent results. The design is not 'weird' or a 'fluke'. Sensitivity is close to, and better than some commercially made superhets. Yes, there is an extra control to be adjusted which is a tradeoff, but for the person who wants high quality mono FM, using valves, with simplicity, there isn't a better receiver. However, the "extra control" can be a set and forget affair unless you're wanting to get every last microvolt of sensitivity for low power or distant stations.

RF Amp & Frequency Converter.
I have found best performance, coincident with ease of construction, results from using a 6BL8/ECF80 at the front end. The triode is used as a grounded grid RF amp, feeding the pentode functioning as an autodyne converter. Having such a low IF means that the signal can be tuned in with the local oscillator either side of the carrier. This can be advantageous if there's an interfering station on a nearby frequency. Image response is a non issue as FM stations do not transmit on adjacent frequencies in any given area.
The original Wireless World article used a 12AT7/ECC81 local oscillator driving a passive germanium diode for frequency conversion, but the gain is obviously lower than an active first detector.

From one of my receivers. Grounded grid RF amplifier feeds an autodyne converter to produce the 200Kc/s IF.

RF Amplifier.
The VHF signal is fed into the triode of a 6BL8/ECF80. This operates as a grounded grid RF amplifier stage and thus suits a low impedance input. RF chokes are used for plate and cathode loads. As such, this stage is untuned and provides not much gain. However, its purpose is to isolate the aerial from the following stage; which is the autodyne frequency converter.
The aerial needs to be isolated, otherwise aerial loading effects will cause the oscillation level to vary excessively, to the point of causing the oscillator to stop in some instances.
It also reduces local oscillator radiation from the aerial.

A characteristic of the 6BL8 is that there is an internal shield between the triode and pentode. It is connected to the pentode cathode. With the original intended use of this valve as a mixer in a TV tuner, the pentode cathode is earthed, and therefore so is the shield. However, in this circuit, the cathode is floating at RF and the shield becomes ineffective. This means there is stray capacitance between the triode plate and the pentode cathode. It appears this is the cause of an interesting effect, which is that at the 108Mc/s end of the band sensitivity actually drops off with the RF amplifier operating at full gain. Yet, at the 88Mc/s end of the band, full gain of the triode is required.
It is the intention that the VHF signal is coupled from the triode plate to the pentode grid via the 10pF and 22pF condensers. But, when signal is fed to the pentode cathode as well (via stray capacitance), it's out of phase with that fed into the grid and so the effective input signal is reduced. Obviously, the stray capacitance has more effect at the higher frequency end of the band.

The result of this is that, ironically, the RF amplifier triode needs to run at reduced gain or be cut off entirely, if full sensitivity is to be had at the 108Mc/s end. The stray capacitance between the triode cathode and the the pentode is sufficient to couple the signal through into the mixer. In fact, for those that want to simplify the design, the aerial can be connected into the tuned circuit by a 1.5pF condenser and this will give the same sensitivity at the 108Mc/s end. However, gain drops towards the 88Mc/s end. One could use the triode for some other function in a simplified receiver.

The upshot of all this is that if full sensitivity is required at the 108Mc/s end, an attenuator of a few dB has to be connected at the aerial input, and removed for reception at the 88Mc/s end. The proper way to do this is of course, to include AGC, so that the RF amplifier gain is reduced or increased as required.
It is quite possible that if separate isolated valves were used for the RF amplifier an converter, this peculiar effect would not occur.

The cathode and plate chokes are not particularly critical. If a balun is used at the input for 300 ohm balanced input, the cathode choke is not required as the balun provides DC return. See the first version circuit. Preliminary tests seem to indicate the plate choke can be replaced with a 10K resistor, but detailed measurements have not been taken with regards to this.

Frequency Converter.
The frequency converter is of the autodyne type; that is, the mixer is self oscillating. Only one pentode (or triode) is required. Here, the pentode operates as an electron coupled oscillator by virtue of the cathode choke and the stray capacities in the valve. The tuned circuit feeds the grid. It determines the frequency of oscillation. Conveniently, because the IF is only 200Kc/s, the received frequency is so close to the oscillator frequency, that we can use the same tuned circuit for both tuning the RF input as well as the oscillator. While the tuned circuit is not right on the received frequency, the selectivity of this circuit is such that a signal 200Kc/s away is not attenuated.
The operating point of the converter is important. Best conversion efficiency (and thus sensitivity) occurs when the oscillator is operating at a low level; just above the point where oscillation starts. Because the oscillator level varies across the band, it is necessary to adjust for the optimum operating point, and so a control (the 50K pot) is provided to vary the screen voltage of the pentode. For strong signals, the operating point is not so critical and the control only needs to be set once.
Because of the low IF, very strong signals can actually cause oscillator pulling. That is, the local oscillator actually locks to the signal, and as a result there is no difference between the local oscillator and signal frequency. Thus, no IF is produced.  To prevent this, I have included AGC to reduce signal strength to below that which causes oscillator pulling. The negative voltage present at the limiter grid is used to reduce the gain of the RF amplifier.
Due to the low IF, the plate load of the pentode is a 22K resistor, rather than a tuned circuit. This feeds the IF amplifier which subsequently provides the necessary selectivity.

IF Amplifier.
The original Wireless World article used a two stage IF amplifier using 6BX6/EF80 valves with the response as shown:

Gain is about 4000, and input voltage (to the IF) should be at least 1mV for optimum performance of the following limiter and detector. However, the converter gain is high, so the receiver works well at signal levels much less than this.
So how do we get this response with no coils? It's quite easy actually when you consider valve input and stray capacitances.  Each of the 6BX6's has a 4.7K resistor in series with the grid. In conjunction with the grid capacitance there is a degree of low pass filtering. The high value of plate resistors (18K), adds to this and so we have the top frequency response set to around 250Kc/s.
The low frequency response is set by the 270pF grid coupling condensers in conjunction with the 100K grid resistors. It starts to fall off at about 20Kc/s.
In the receivers I have constructed, I have departed from the Wireless World IF amplifier design in some instances, but the results are the same.

Complete IF amplifier, limiter, and detector. The .47uF can be reduced to .22uF or .1uF for faster acting AGC.

Limiter and Detector.
Limiting is done in the conventional way with a third 6BX6 operating with low bias and a low value plate load. Because of the low frequency used, it is quite easy to observe the waveform with a CRO throughout the IF, limiting and detection stages. Because the limiter is operated with a low bias, the signal fed into the grid causes grid current to flow, and thus produces a negative voltage which is consistent with signal strength. This negative voltage suitably filtered can be used for AGC and to drive a magic eye tuning indicator.
The clipped waveform from the limiter plate is differentiated, and applied to a pulse counting, or tachometer, circuit. The higher the frequency, the closer the pulses are together, and the the higher the resulting DC from the detector, and vice versa as the frequency decreases. So, we have a frequency to voltage converter which is what we want for FM demodulation. The greatest advantage is there are no tuned circuits to get out of alignment, causing distortion.
Despite its appearance as a voltage doubling AM detector, the circuit around the 6AL5/EB91 is anything but. The low value input condenser (47pf) and the low value load (4.7K) ensure the signal from the limiter is differentiated. Filtering is done with a simple RC circuit which also provides de-emphasis.
Audio output is low at about 100mV, and the recommended load is 500K. While an ordinary triode pentode audio amp can be just fully driven, an extra stage of gain is worthwhile.

First Version.

First Pulse Counting FM Receiver, Winter 1990. This is my Super DX model with 3 stages of IF amplification.  Valves are, from back to front, 6V4, 6BM8,6AU6 x 4, 6BL8 and 6AL5. The magic eye is an EM84.

Under the chassis of my first pulse counting receiver.

Circuit of original receiver. The 15uH choke in the RF amplifier cathode circuit is not actually required as the balun provides DC continuity.

I had the basic receiver assembled in one evening, and due to my scepticism, I'd added an extra IF stage in case the gain turned out to be inadequate. I was in a state of amazement when I first powered it up, and was getting Hi-Fi sound with excellent sensitivity. The following night I'd added a grounded grid RF stage to eliminate the problems of aerial coupling and absorption effects. With an indoor TV aerial I had no problems in bringing in all local stations, and the low power community broadcasters that caused so much difficulty on the super-regen sets. And there was no SCA/stereo subcarrier beat, no hiss, and no distortion!!
Subsequent experiments proved that stereo reception was not practical. It appeared that the demodulated signal is not of sufficient bandwidth, and to increase it would mean reducing the output. However, with high frequency boost prior to the LM1310 stereo decoder, it was possible to get results of some sort but separation was just too poor.

I did some simple tests with my first receiver, with the three IF stages, and a Hewlett Packard 8654B signal generator. Even with no aerial connected there was some difficulty in finding a clear frequency in the middle of the band as stations just roll in from everywhere. My initial tests were done at about 90Mc/s, with a 1000c/s tone. Deviation was set to 70Kc/s. 1uV was discernible, but only just. Had it been voice or music you wouldn't be able to understand it. 3uV was better; just readable. At 10uV, the signals are very readable. Noise free reception commences at about 30uV. Not bad for an FM receiver with only one tuned circuit! For the limiter to start clipping, signal strength required is much greater; around 500uV. However, this is not important as VHF is not prone to interference.
I also examined the performance if the oscillation level control, which sets the frequency converter's operating point was simply used as a preset control. Much to my surprise, the change in sensitivity was not as great as first thought as I tuned across the band, maybe a loss of 10uV or so. Interestingly, this seemed to be around the centre of the band.

AGC and Magic Eye

AGC was added to this receiver in October 2018 in order to optimise sensitivity for distance reception (see the description above). In this receiver, the grid of the 3rd IF amplifier is used as a source of negative voltage. With the other receivers having a two stage IF amplifier, the grid of the limiter is used instead. Attempts to use the limiter grid in this receiver were difficult because the higher gain of the IF strip meant that the noise level was high enough to create a permanent negative voltage even when the receiver was not tuned to anything.
Experiments with various delay circuits were carried out but the result was not as it should be. Further thought indicated that a negative voltage dependent on signal level should be available at the third IF amplifier grid. While it is true the IF amplifiers are mostly operating in class A, if the input signal is greater than the grid bias, then grid rectification will occur. Indeed it does, and the voltage is just right for the purpose. A voltage divider feeds the grid of the EM84 (6FG6) magice eye so that the eye is just about closed with a 1mV input signal.

2nd Pulse Counting Receiver.

Second Pulse Counting Receiver, October 1992.

This receiver uses  6SN7's for IF amplification, and also uses a 6SN7 fed by a 12AX7 for the audio amplifier. The resulting 'triode sound' is the nicest sounding of all my FM receivers. A series heater circuit is used with modern low voltage transformers for the power supply. This receiver was operated daily for several years at my place of work and never failed.

Under the chassis of the 2nd receiver.

A later modification was the addition of AGC, and more recently a magic eye tuning indicator.

Unmarked heater bypass condensers are 0.15uF.

The circuit differs from the other designs in that it uses triodes for the IF amplifiers. The operation of the frequency converter is stabilised by a 62V zener diode. Prior to including this, the receiver would be susceptable to oscillator drop out - particularly on weak stations where the converter is only just oscillating. The main power transformer was obtained from a solid state 1970's stereo amplifier. The 6.3V winding supplies a little more than 6.3V, hence the 0.47R resistor. The 29V winding supplies the 6SN7's and 6BL8 in a series heater circuit. The 12AX7 is supplied separately through its own dropper resistor. Note that 6BL8 is not a series heater type, and nor are standard 6SN7's. Unless 6SN7GTB's are used, there is the chance of unequal heater voltages. In my set, the audio 6SN7 needed a 220R 1W shunted across its heater. The two 82R 1W resistors shunt the extra 150mA from the 6BL8 with its 450mA heater.
High tension comes from another transformer used in reverse which feeds a bridge rectifier. This came from a piece of computer equipment. The output transformer is a Jaycar MM1900 with the 1W tapping used.
The 30pF variable condenser between the RF amplifier and tuning coil is a Philips beehive type. It adjusts the signal coupling but can be replaced with a 10pF fixed condenser as per the other receivers. The heater bypass condensers shown are mounted right at the valve sockets.

Third Pulse Counting Receiver.

The third pulse counting receiver I built is for 12V operation. It uses a vibrator power supply. Tuning is by a ten turn pot and varicap diodes. Its valves are 2x 6U8, 6BX6, 6DX8, 6AL5 and 6BQ5. It provides the highest audio output of all my pulse counting receivers. While it has good sensitivity and sound quality, the varicap diodes cause drift, as the set warms up over about 20 minutes. An AFC circuit will have to be provided, or a return to variable condenser tuning, to eliminate this.

 4th Pulse Counting Receiver

This set was constructed in the Winter of 2000. It was constructed in a plastic instrument case to make a compact and portable receiver. Initially, I used a 6DX8 for the audio, but the heat generated inside the case was too much and so I changed to a 6BL8 with its lower heater and plate current. Extra ventilation holes also had to be drilled.

Note the revised audio amplifier. It is not recommended that constructors use the power supply circuit shown. No responsibility taken for fatal electric shock due to incorrect construction techniques.

The power supply is unusual as far as Australian design goes, using a live chassis with a transformer for the heaters only. This was done for space reasons. There was no way any valve type power transformer capable of powering this circuit could fit in the box with everything else. For the B+,  the 240V mains is rectified by a 1N4007 and smoothed with RC filtering. No hum is evident even with sensitive headphones.

Very compact inside with 6 valves! On the left are the front end valves. The bottom row is the 6BX6's, and the 6BL8 converter and 6AL5 are on the top. Over at the right is the 6BL8 audio valve.  This receiver has a live chassis and has suitable precautions to prevent the user coming into contact with the mains.

One thing that happened was the dropping out of the oscillator at the high end of the band. I eventually discovered it was due to the original 1.5mH cathode choke. For some reason the one I'd used wouldn't allow proper oscillation. Changing to a different type (axial 1mH) fixed that completely.

Some notes for constructors:
1) Resistors: 1/2W unless specified.
2)Capacitors: Values in pF unless specified, or less than 1uF. For example, .1 is .1uF. Use ceramics for the pF values. As the IF strip is working at
   around 200Kc/s, polyesters can be used in that area, but I have used ceramics for the lower values because of convenience. The voltage rating should
   be obvious. Obviously, the ones that are exposed to the full B+ before the valves warm up need to be rated thus. Cathode bypasses obviously don't need
   such a high voltage rating.
3)The tuned circuit: Among the most often asked questions. It's the same as the other valve receivers on this site; 4 turns of 18 gauge tinned copper wire, air cored, 10mm diameter.
   It is tuned by a variable condenser of around 15 to 20pF max capacitance. Higher value condensers can be used with an appropriate fixed series condenser;
   e.g.; 39pf fixed in series with 60pF variable. Varicap diodes can be used but steps need to be taken to minimise tuning drift.
4)The audio stage: The output of the detector filter is meant to run into a 500K load; hence the value of volume control shown. Output voltage is around 100mVrms.
    Do not feed into a solid state amplifier unless you incorporate a impedance matching stage such as a cathode follower.
5)Power supply: 6.3V @ 2.1A; subtract 450mA if you're not using the 6BL8 audio amplifier. High tension: 180-190V @ 14mA for the 6BL8 audio amplifier.
   205-220V @ 25mA for the receiver itself. If you can't design your own power supply you should rethink any ideas of building this receiver.
6)Aerial: Unbalanced input. Suits 75 ohm aerials. Use a TV balun for 300 ohm balanced transmission lines and aerials. A length of wire is not a proper aerial unless you are in a very good signal area.  An outdoor multi element yagi or log periodic is preferred. Telescopic TV aerials will suffice if an outdoor aerial cannot be used, but obviously the results will not be as good.
7)Construction: Stating the obvious, but the usual VHF techniques apply; a proper ground plane, short leads, etc. Twisted pair heater wiring is used. One side is earthed only at the 6BL8. All heaters are to have a .1uF condenser connected across them. This can be 100V polyester/MKT. Modulation hum of feedback between stages may be evident if this is not done.

Ideas which I haven't actually implemented but are worth experimenting with. Note that these in no way imply this is an unstable receiver that suffers from drift. They are merely good practice to include in any VHF receiver.
1)AFC: The DC present at the detector output or perhaps the DC on the AGC line could be used to provide AFC as these voltages peak up on correct tuning. Varicap diodes or using the miller effect of a triode could be used to control the oscillator frequency. I did experiment with a varicap diode  fed from the detector output with my first receiver and the idea seemed to hold promise.
2)Regulating the B+: When the mains voltage changes and the receiver is adjusted to just past oscillating for the most sensitive point, it may drop out when the mains voltage decreases. Regulating the B+ to the converter stage at least would overcome this. Also, the frequency at which the 6BL8 pentode oscillates is affected by plate and screen voltages (the screen control can actually be used for fine tuning within limits). Regulation would therefore improve frequency stability.
3)Regulating the 6BL8 heater: I have noticed that after a large drop in mains voltage that within a few seconds the receiver may drift off frequency. The time delay suggests the heater temperature of the 6BL8 pentode has an effect on oscillation frequency. So, it would be worthwhile to provide a regulated supply for this as well. Easiest way is with a three terminal regulator set to 6.3V. As the regulator has to be fed with DC, consideration has to be given  to  the other heaters. Two options are: a) separate heater windings (or separate heater transformers), one feeding the other valves with 6.3VAC and the other feeding the bridge rectifier and regulator (it will need to be about 9V to allow for regulator headroom and rectifier losses), b) one winding feeding a rectifier and regulator to provide DC for all the heaters. The reason for separate heaters is of course with bridge rectification one cannot earth both the input and output of the rectifier, and it is essential that one side of the heater line is earthed.
4)Automatic level control for the oscillation amplitude of the frequency converter. This would eliminate the "extra control". Other kinds of frequency converter could also be investigated; e.g.. pentagrid valves, or separate oscillator and modulator valves.

Thoughts on Stereo:
An attempt was made to connect an LM1310 type stereo decoder to the original receiver. If you wish to experiment, connect the decoder input to the junction of the two 47K resistors in the detector output filter. Change the 1000pF to 100pF. Although results of a sort were obtained, separation was poor, and stereo reception was unreliable. Later research revealed the problem is lack of bandwidth with the pulse counting detector as presented. Don't forget the design was optimised in an era when multiplex transmissions had not been thought of. Don't forget that the stereo signals are centred about 38Kc/s, hence the need for greater detected bandwidth. Detected output voltage, and bandwidth of the detector is dependent on the value of coupling condenser from the limiter to the detector diodes. The larger the condenser, the wider the pulse,  the higher the output, and the the narrower the bandwidth. So, if you have ideas about trying the design for stereo reception, a good start would be to reduce the 47pF, as well as the filtering on the detector output. However, the detected output will now be of lower amplitude. It would appear therefore, to compensate for this, the B+ for the limiting stage will need to be increased. This may mean the 6BX6 will be outside its ratings, and if so will be necessary to change the limiter valve to something higher powered. Having said all that, the Zenith stereo multiplex system used for FM stereo is a limited performer to start with, and requires a signal far better than that required for good mono reception.

Version 5 Pulse Counting Receiver.

This receiver was the first where I'd included a magic eye tuning indicator. It is based on my original version, but with one less IF stage. To enable the 6BM8 to be driven with gain to spare, an extra audio stage has been added. It is simply a 6AU6 wired as a triode, and the cathode resistor is unbypassed, as only a low gain is needed.
I have also taken the opportunity to try my homemade VHF chokes as the originals are almost impossible to obtain. Constructors of my VHF receivers have difficulties in getting the original commercially made chokes I used, and often the substitutes perform poorly or stop the receiver working altogether. So, now this problem has been solved. I now recommend the homemade chokes for all the valve pulse counting designs in all three positions. The same goes for the super regenerative sets. Because the power transformer only had a 2A 6.3V winding, it was necessary to include another filament transformer for the 6BM8/ECL82 and 6FG6/EM84
The magic eye is very useful for tuning, and as a relative signal strength indicator. It also makes it very clear when the 5K oscillation level pot is adjusted optimally.
Note that the screen grid voltage for the frequency converter is fed from the same B+ point as the RF amp which is AGC controlled. The common 2.7K resistor means that the screen voltage fluctuates with signal strength, and this reduces the necessity to adjust the 5K pot. For local stations it is possible to leave the 5K pot preset.
Note also the extra components in the screen circuit; the 10K and .15uF and .082uF. These were only included because of the wiring distance to the 5K pot in this particular receiver - they are not normally needed as the previous circuits show.

Circuit of the 5th Pulse Counting Receiver. This incorporates an extra audio stage needed to drive the 6BM8 to full power. A magic eye simplifies tuning.
2 detectable
5 -0.95 noisy
8 slight noise
10 -1.49
12 -1.7 noise free
20 -2.44
50 -4
100 -5.55
200 -7.08
500 -8.84
1000 -9.93
5000 -12.24
10000 -19.8 magic eye closed

This table shows ACG voltage versus signal input. Frequency was 100Mc/s, deviation 50Kc/s, modulation 1Kc/s. 5K pot was adjusted for maximum sensitivity at the start of the test. Signal generator was a R&S SMS.

This is the best performer so far. It also includes the often asked for magic eye circuit. It follows the original circuit in that 6AU6's are used for the IF and limiter, but there is one less IF stage. This is because in the original receiver this contributed more noise than gain. If you think you're seeing 43K resistors in the circuit, you're right - they were to hand so were used. 47K is suitable instead.

From another constructor:

This Pulse Counting Receiver was made by Josef from the Czech Republic.

It uses the EF80 IF amplifier stage and includes the EM84 magic eye. The power supply is external and connects via an octal socket at the back.

I thought this was a particularly good example of correct construction technique. As can be seen, wiring is kept short and direct. The aluminium diecast box makes an excellent chassis for RF projects such as this. The particular box used was this
You can see the YouTube video here It gives a good idea as to how the receiver operates.

The RF chokes.
One of the most common questions I am asked is about the RF chokes. There are three in each of the different circuits. Two are used for the RF amplifier, as cathode and plate loads. A third is present in the 6BL8 pentode cathode circuit, to make this valve oscillate. The two RF amplifier chokes are not particularly critical, and many kinds of VHF choke can be used here. As can be seen, commercially made chokes of 15uH or 20uH have been used in the RF amplifier cathode circuit, and 8.2uH in the plate circuit. The 6BL8 pentode (frequency converter) circuit has used 1mH or 1.5mH chokes.
If you have these chokes to hand, by all means try them.
However, it has been found, as with the super regenerative receiver circuits described elsewhere on this site, that the home made chokes are better and provide consistent operation. I now recommend that they be used for all three positions, with the 6BL8 pentode being of first priority. The chokes are made by winding 75cm of 25 gauge enamelled copper wire on a plastic former of about 6.3mm diameter.
75cm represents a quarter wavelength at 100Mc/s (i.e. the middle of the FM band), and so are at their highest impedance around this frequency.
Note that measuring their inductance will reveal something close to 2uH. However, the chokes are operating because of their quarter wavelength characteristic and are not chosen for the inductance value.
Therefore, take no notice of the inductance values shown in some of the circuits when using the home made chokes.
Note that if oscillation seems poor, the connections to the 6BL8 cathode choke may need to be reversed. This is because of magnetic coupling to the tuned circuit, and or RF amplifier. If the coupling is in the wrong direction, it will cause negative feedback, and thus a reluctance to oscillate.

An Analysis of the Pulse Counting Receiver.
From the U.S., another constructor Brian White, did some interesting simulation and measurements, particularly with the IF amplifier. Also, for those interested in a monostable multivibrator detector, he's done some design work and created a working example.
See here for further details