This project came about mainly as a result
of collecting a quantity of 902 CRT's over the years. Added to that, I
have a particular fondness for electrostatically deflected TV sets.
Despite the apparent simplicity of the final design, there were a number of difficult challenges to overcome.
From left to right, top to bottom, controls are: Focus, Brightness, Line Hold, Frame Hold, On/Off Volume, Contrast.
With the cessation of analog TV transmissions in December 2013, it was considered pointless to include an RF front end in the design. Instead, the audio and video signals from a DVB-T receiver would drive the unit. In this regard, it is probably more correct to call it a video monitor, although with the digital receiver it is still a complete off air receiving unit.
Only for sentimental reasons or for reproducing an old design, is it worth making up a tuner and IF strip because this will necessitate a modulated RF output from the signal source anyway. As I was not aiming to recreate a vintage piece of circuitry, there was no question in omitting it.
Signals are provided by a DVB-T receiver. Of course, a VCR, DVD player, camera, or any other video source can be used.
The 902 (or 902-P1) cathode ray tube was
released in 1938 by RCA, intended for low cost oscilloscopes, and a few
American magazines of the era describe homemade TV receivers using this
tube. It is octal based with a 2" green screen of medium persistance
(P1 type phosphor). These TV designs used simple thyratron timebases, driving
the deflection plates via a single stage amplifier. The RF front end was
simple with a mixer/oscillator circuit feeding a couple of stages of IF
amplification. With the highest TV channel not more than about 60Mc/s,
octal valves of the time worked satisfactorily in strong signal areas.
Off air reception on the 2" TV receiver.
Having built the Radio Television & Hobbies 5" TV receiver using a 5BP1 tube back in 1984, electrostatic sets are no stranger to me. I also have a commercially made example, a Sentinel 400TV
Initial thoughts were for a two stage pentode video amplifier (required to preserve video polarity as the 902 is grid modulated), a single pentode sync separator, thyratron timebases and triode or pentode output stages, depending on gain required. Audio would use a simple triode/pentode arrangement. Physically, the chassis would be as compact as possible. Modern valves would be used simply because I don't have enough 2.5V heater 6 pin base valves to use for new projects (or the power transformer required).
I had a CRT demonstration unit, made up
many years ago by a staff member at my work, which conveniently used a
902 CRT. This simply applies the correct voltages to the tube and allows
one to demonstrate the shift, focus, and brightness controls. This allowed
me to familiarise myself with the voltages required to drive the tube,
and to get an idea of brightness and focus.
For the thyratrons, I tried 2D21's. These are a modern industrial 7 pin pentode type and I have a good quantity of them. Results were not particularly good, but as they weren't designed for timebase use this is not surprising. The problem was jitter with the 50c/s frame oscillator, and I could not get good oscillation at 15,625c/s for the line timebase. Type 884 would be better, being designed for timebase use. Regardless of type used is the non linear sawtooth which would require correction for an acceptable TV picture. Then there was having to provide for 600mA heater current for each 2D21. With these disadvantages, I changed the design to use Miller-Transitron oscillators. This would simplify the timebase design, providing a perfectly linear scan, and possibly drive the CRT plates directly. Experiments seemed to confirm the output voltage was high enough to do this.
Now that I knew what valves were required, a chassis was designed, punched, and bent up. Given the small power transformer, considerable thought was given to minimising heater current and this determined the valve types used.
Here, I used 6BH6's where possible. These are roughly similar to a 6AU6 but with half the heater current, at 150mA. A similar low current heater type is the European 6CQ6/EF92. The video output would use a 6AK6, again a 150mA heater type, similar to the European 6AM5/EL91. For the audio, a 6AB8/ECL80 was chosen.
The set would be constructed on an aluminium chassis with a black Marvi-Plate front panel. The CRT was to be supported at the front simply by it resting in a hole in the front panel lined with plastic edging strip. So that the tube could be rotated, an Amphenol type octal socket with spring clip was used at the other end.
The fun begins...
The initial timebase and sync circuits were based on designs appearing in Practical Television during the 1950's, when electrostatic TV sets made from disposals components were very popular. With a theoretical circuit drawn up, the set was wired thus. With the compact design, I used tagboards as well as tagstrips for the component mounting. Upon first powering up, things were not always what they should be. This is not surprising, but to solve all the problems took more work than expected.
At this point it is best to show the final circuit and explain each of the stages and their development.
Final circuit of the 2" Television. Note there is a mistake - pins 4 and 6 on the 902 connections need to be swapped otherwise the picture will be reversed. The 220K 6AK5 plate resistor can be taken to the 350V supply for increased output and better locking of the line oscillator. Improvement in contrast control range can be obtained by connecting a 470 ohm resistor in series with the contrast pot, or alternatively using a 2K or 2.5K pot.
The 902 Cathode Ray Tube.
My 902-P1 tubes were looking for a use...
A limitation of this tube is the common
between one of the X and Y deflection plates, presumably because the octal
base simply does not allow for separate connections. This means the deflection
has to be of single ended drive. I had heard of distortion with tubes so
driven, but apparently the small size allows one to get away with it. In
practice, the effects are minimal on the TV picture. There is a small amount
of trapezoidal distortion if one really looks for it.
The CRT was found to be very susceptible to hum pick up from the transformer. In ordinary oscilloscope use this would not be noticed, but the TV picture suffered defocussing and raster distortion modulated by the magnetic field. Luckily I had supplied with one of my 902's a shield made from steel pipe. This was mounted on the chassis and solved the problem. Without the shield, the transformer would have to be mounted remotely.
The application notes show the CRT operated with negative EHT. This is standard with CRO circuits as it allows the deflection plates to be at earth potential. However, this requires the CRT's heater supply to be isolated. This along with extra complications with video modulation means it is better to use the tube in a more conventional manner.
One problem was very evident and that was the picture would shift depending on brightness. I could not see a logical explanation for this, and have certainly not had the effect with other tubes. I can only put it down to the common plate connection. Indeed, the voltage here was found to be varying with the beam current.
RCA's application data for the 902.
The voltage divider I used to derive the
CRT potentials was based on the RCA design but modified for positive EHT.
However, with the final anode/common plate connection varying relative
to the other deflection plates it was obvious some kind of regulation was
required. Regulating the EHT did not fix the problem. Somewhat better results
were obtained by regulating the anode/common plate connection (pin 1).
Ultimately, I regulated the shift voltage relative to pin 1 by 75V zener
diodes. The plate voltages no longer shift relative to each other depending
on beam current, and the problem is fixed. The .22uF is required
for bypassing. Without it, the X and Y plates modulate each other through
the common connection resulting in a very peculiar distortion.
The focus and brightness controls are conventional, but a DC restorer circuit has been included. It is necessary to grid modulate the CRT because the cathode is common to the earthed heater pin. Cathode modulation would require a low capacitance isolated heater winding.
This part of the circuit is straightforward and presented no problems. Incoming video is terminated in 75R to present the correct load to the signal source. Voltage here is 1V p-p.
Two stages are needed, because of the incoming video polarity and that the CRT is grid modulated. I loosely based the design on that used in the 5BP1 TV set. Both pentodes are operating as ordinary RC amplifiers. Frequency compensation is provided to obtain sufficient bandwidth. The 1000pF bypasses the 180R cathode resistor for the 6BH6, thus increasing gain as the frequency rises. The 6AK6 stage is compensated by including an 82uH choke in the plate load. As gain of the stage increases with plate load resistance, we can see that as frequency rises, so does the effective plate load. Measured bandwidth is about 2.5Mc/s which is more than enough for the small screen size. Contrast control is provided by varying the cathode degeneration of the output stage. It is done here so the amplitude of video fed to the sync separator is always at maximum amplitude, and to provide constant bias for the 6AK6. Bias for the 6AK6 is grid leak, relying on the positive going sync pulses to charge the .1uF coupling capacitor.
With no video signal, the plate and screen resistors limit valve dissipation. 4.7uF capacitors bypass the screen grids providing sufficient low frequency response. Drive to the CRT is around 30Vp-p. There is more than enough gain, and normally the contrast control is operated at maximum resistance (lowest gain).
Philips PM5544 test pattern as displayed on the front of the 902-P1. At right is the 6AK6 plate waveform with the test pattern displayed at maximum contrast.
Most simple and/or low cost sets feed the video to the CRT grid or cathode capacitively. This makes for a simpler design because video amplifier operating conditions and signal strength do not affect the brightness. Also, contrast and brightness controls operate independently of each other. However, it will be noticed that the average screen brightness remains the same, regardless of scene content. For example, the screen is still lit up during a night scene.
I had seen mention of simple diode DC restorer circuits many times in the past and had been intrigued by them. Given the ease of incorporating one, I used the construction of this set to try out the design. Results were obvious. With no DC restoration, and a DC coupled CRO on the grid pin, the DC level fluctuated with scene content as expected. With the DC restorer, it remained largely constant. The effectiveness is even more obvious when the video signal is removed - the screen is virtually blanked out.
At the plate of the 6AK6, the video signal contains negative going sync pulses. The voltage across the .01uF charges up to the sync pulse tips by means of the 1N914 diode.
This keeps the CRT grid at a constant DC voltage. The brightness control merely offsets this voltage as required. Of course, a valve could have been used, but with limitations on heater current, the solid state diode was preferred.
Miller-Transistron timebases were only popular in the UK and only then for a short period in the late 1940's-1950's. This is surprising considering how simple and effective they are.
I had first used such a design in the frame timebase of the 5BP1 TV set, so knew of its excellent linearity.
It is probably the only non thyratron single valve timebase not requiring any inductive components. Oscillation occurs because of positive feedback between the suppressor and screen grids. The sawtooth component comes about because of the capacitor between plate and control grid. The capacitor is effectively charged at a constant current because of the amplification of the valve. Oscillation frequency is determined by this capacitor and the grid resistors. Sync pulses need to be negative going.
From left to right, the valves are 6AB8 (audio), 6BH6 (frame), 6BH6 (line) and 6AK5 (sync).
A lot of trouble was experienced trying
to get sufficient scan amplitude. While the screen, suppressor and plate
resistors all affect amplitude, it was found there simply wasn't enough
available to fully deflect the 902 even with all component values optimised.
Deflection senstivity of this tube is not very high, and having to use
single ended drive makes it harder.
I did try experimenting with adding triode amplifer stages but without success. For one thing, linearity was ruined and attempts at correcting it reduced the amplitude. It was becoming obvious that the limiting factor was the amplitude was limited by the saturation voltage of the valves. Attempts to 'force' a greater output simply resulted in picture foldover where the sawtooth bottomed out. Obviously, 300V B+ was not enough. Raising this to 350V solved the problem, with full width and proportionally high frame scan.
At left is the waveform for the frame oscillator plate, and at right is the the line oscillator plate.
It might be wondered about the differences
between X and Y plate sensitivity. Indeed there is a difference because
of one set of plates being in front of the other and thus further from
the cathode. While it was actually possible to improve things by swapping
the line and frame plates, the end result was a reversed picture!
It should be pointed out here that the Miller-Transistron circuit provides a negative going sawtooth - the opposite to the positive going 'textbook' sawtooth. This is not problematic as long as both timebases produce the reversed waveform, as the CRT is simply rotated 180 degrees for correct picture orientation.
Because of the common plate connection in the 902, one has to use pin 6 for frame deflection, and pin 4 for line deflection for the picture to appear the correct way up.
Under the chassis. Along the top is the timebase and 350V supply circuits. Down the middle is the audio and video stages, and the power supply. Along the bottom is the EHT circuit.
This was the most difficult and time consuming section to design. The problem was worsened by the Miller-Transistron timebases needing a high amplitude negative going sync pulse, and the low gain video stages. In a commercially made set, the sync separator is usually fed from the video output stage with about 60V p-p of video. This makes for easy sync separation as the sync separator grid is driven hard into conduction.
Initially the circuit was a simple pentode sync separator, based on early Practical Television designs. It was fed from the plate of the 6BH6 video amplifier, but it was not driven hard enough into conduction, with video still present in the output. This of course caused locking dependent on the picture content. While a higher gain video amplifier would have helped, it would have required valves using more heater current. Using the 6AK6 to drive the sync sepator was experimented with, but the problem here was the video polarity was incorrect. The sync separator must have positive going sync pulses to charge the grid capacitor. It's this capacitor charging current we want to drive the grid into conduction.
A limiting factor in all this was of course having only one valve for the sync circuit. Having already built the chassis, it would have been difficult to add another valve with little room to put it. Any usable dual section valves require a 9 pin socket and due to the location it was not practical to replace the 7 pin socket with one.
I then started experimenting with diode sync separators. These had gone out of fashion in the 1940's, but the simplicity was attractive. The concept of a diode sync separator is simple. If a video waveform with positive going sync is fed into a diode via a capacitor, the capacitor charges up to the peak voltage which is that of the sync tips. Now, if a resistor is placed across the diode so as to discharge the capacitor between sync pulses, then the capacitor will charge everytime a sync pulse comes along. The diode charge current appears across the diode load resistor and here the sync pulses are available.
The circuit is really a modified DC restorer and by this means, the sync pulses are unaffected by the luminance component of the signal.
It can be seen that this kind of sync separator has no gain. If for example the incoming waveform is 1V p-p, the sync will be 300mV peak at best. For this reason, I used a germanium diode to keep voltage drop to a minimum. As with the picture tube's DC restorer, a valve diode could have been used.
Results were good and at last clean sync pulses were available, with the sync separator fed from the 6BH6. However, being a fraction of a volt they are completely inadequate for triggering the timebases. Here, the existing pentode was used simply as an amplfier, conveniently inverting the pulses as well. Because of the repetitive waveform, grid leak bias can be used, saving the usual cathode bias components. Initially, a 6BH6 was used but even after optimising the screen and plate resistors, gain was not really enough. How to increase this? Then I remembered the 6AK5, pin compatible in this circuit, and with similarly low heater power. Sure enough, with a 6AK5 in circuit, gain was much higher and locking improved. Further improvement was had by taking the 6AK5 plate resistor to the 350V supply.
6AK5 plate waveforms. At left is at line rate, and at right is viewed at frame rate.
At the 6AK5 plate are negative going line
and frame sync pulses. The frame pulses are integrated with a .22M and
470pF to remove the line sync. The resulant pulse triggers the frame oscillator
via a 2200pF connected to its suppressor grid. Line pulses are fed via
20pF to the suppressor of the line oscillator. It should be noted that
to look at the waveform it is necessary to remove the timebase valves.
This is because the suppressor grids of the Miller-Transistron oscillators
feed their own signal back out into the sync separator.
One problem noted was that the sync amplitude required for good locking increases with increased amplitude of the timebases. It was found locking was better when the timebases operated off 300V as compared to 350V.
As well as this, ripple on the power supply caused problems earlier on. With a ripple voltage amplitude not much different to that of the sync pulses, it was not surprising to see the frame oscillator trigger on the mains instead. Once this was attended to, frame locking was quite good.
I used a 6AB8/ECL80 because of the 300mA heater current. This valve was not popular in Australia but it was used in a few English designed TV sets sold here. An interesting characteristic is the common cathode between triode and pentode sections. The triode section is mounted above the pentode using the same cathode sleeve. Although the grid bias specification is different for the triode and pentode sections, with a simple audio amplifier like the one used here, the triode bias conditions are non critical enough not to require a separate bias supply. Negative feedback is provided by the 2.7M resistor between plates. The output transformer is a 100V line transformer, Jaycar type MM-1900. Output power is 620mW with frequency flat within 3dB from 290c/s to 8Kc/s. Because most signal sources provide stereo, a resistive mixer is used prior to the volume control to create a mono signal. Given the low impedance of most signal sources, a 10K volume control was used. As an alternative to the 6AB8, I could have used a 12AT7 as was done in the 5BP1 TV set. This also draws only 300mA heater current. Power output and gain would be down, but still more than sufficient for this application.
The design of this was largely determined by the AWA power transformer I had. It has a single 285V winding with no centre tap, which meant half wave rectification was in order, if a valve rectifier was to be used. It also has one 6.3V winding for the heaters. The current ratings are unknown, but judging by the core size, I estimated it would handle about 60VA. At a rough guess, heater current rating was assumed to be around 2-2.5A. B+ would probably be 60mA or thereabouts. As the B+ drain would not be particularly high, it was assumed there was some leeway with regards to heater current. Power consumption of the set turned out to be 47W, and the transformer does not run particularly hot after several hours.
The 240V mains supply is also fed to a three pin socket on the back of the chassis. One of the annoying things about having to use digital boxes is that another power socket has to be provided. Seeing as this set would always be used thus, it made sense to include it on the set. The socket is switched by the same on/off switch for the set itself. This means the digital box is only powered up when the set is turned on. The power transformer primary is fused at 400mA, and the mains socket at 3A. The socket is fused simply to protect the on/off switch contacts in case of a shorted digital box, or someone does something idiotic like plug in a radiator or washing machine.
Back of set has a 240V socket for convenient powering of the DVB-T receiver.
The 300V B+ supply comes from a 6N3/EY82
rectifier and an RC filter with two 33uF capacitors. Initially, the filter
resistor was only 470R and this resulted in about 4V p-p of ripple which
caused problems with the sync circuitry, as mentioned before. A 100uF as
the final filter improved this, and trying a filter choke instead of the
470R got the ripple to 1V p-p, and resonating the choke at 50c/s, was even
better. As it eventuated, the choke and higher filter capacitance were
I had overlooked the fact the the 6N3 takes 900mA for the heater, thinking it was only 600mA, and should really have used a 6X4 or 6V4 with the plates joined together instead. However, transformer overheating has not been a problem, so the 6N3 stays.
The 6N3 rectifier is at the far left, with the 6AK6 and 6BH6 video amplifiers to the right. Also visible are the preset centering controls.
The video amplifiers, sync separator, and
audio amplifier are fed from the 6N3 rectifier.
Various schemes for developing the 630V EHT were dreamed up but the most sensible was a simple half wave voltage doubler. Because of heater current availability and that floating heater supplies would be needed, the idea of using valves was dropped. 1N4007 silicon diodes are used instead. The negative going current in the first diode was used to advantage, providing the negative voltage for the brightness circuit. Around -50V is produced here. The EHT is filtered with another RC filter comprising of a 150K resistor and two .33uF capacitors.
As mentioned previously, it was found necessary to provide 350V for the timebases. The cathode voltage of the 6N3 is not quite high enough, especially when some voltage has to be dropped in the filtering circuit. One option was to increase the current available from the 630V EHT supply and provide the 350V via a dropping resistor. This was tried with some success, but the dropping resistor was wasting about 7W. This was undesirable in the interests of minimising transformer loading. The available EHT voltage was also reduced slightly.
Another option was simply to provide another voltage doubler but for the timebases only. This worked well. To avoid the problems of having to drop around 300V across a resistor, the doubler circuit was designed to put out less than double the voltage when loaded. This was easily done by selecting the input capacitor to suit; the reactance of it limiting the current. A two stage filter was required to get the ripple down to 1V p-p. One problem was that until the timebase valves had warmed up, the filter capacitors would be exposed to excessive voltage. On no load, over 500V was appearing across the 450V rated capacitors. A zener diode clamp fixed this. Note the 75V zener between the 300V and 350V supplies.
The 350V supply is prevented from going 75V above the 300V supply. When the set is first switched on and the valves are not drawing current, the 300V supply is zero because the 6N3 has not warmed up. Thus the 350V supply is clamped to 75V. As the 300V supply comes up to full voltage, and the 350V supply drops, the zener diode no longer conducts.
Because of the small screen size, it's more of a novelty than something to watch a two hour movie on. Having watched television on a 5BP1 for many years, I find the green picture a non issue. The picture really needs to be a minimum of 3" to be of long term entertainment value, however.
Indeed, a lens placed in front of the screen gives a marked improvement. Brightness is quite adequate for a normally lit room, but it is important not to let light fall directly on the screen. Focus is a slight problem given the age of the CRT's, as they are now slightly gassy. Nevertheless, it improves with low brightness settings and is possible to read some subtitles.
For what it is, the picture is remarkably good and it makes a nice desk top TV. An enterprising constructor could build it into a car dashboard, powered from the car electrical system and using a 12V DVB-T receiver.
It is hard to imagine a simpler circuit than the one presented here. None of the stages can be done away with, except for the DC restorer. The audio stage could be simplified using a single high gain pentode. While it couldn't be driven to full output, the volume would still be enough for close viewing. While I have not tried it, a single high gain pentode might work for the video amplifier, if the video was fed into the cathode. Grounded grid operation would preserve the video polarity. The input impedance in this configuration would probably suit the 75R video source quite well. The power supply could be simplified a little; one 350V supply for everything except the EHT. With the present transformer, this would require a silicon bridge rectifier and choke filtering. It is hard to imagine a simpler EHT supply unless a high voltage winding was available, and even then only one capacitor would be eliminated.
Some of the controls could actually be eliminated due to their non critical nature; the brightness, contrast, height, and width controls could be replaced with fixed resistors.
Typical off air picture. Again, some quality is lost in taking the photograph.
See the set operating at my You Tube site here.